Integrated circuit tester with high bandwidth probe assembly

ABSTRACT

Described herein is a probe card assembly providing signal paths for conveying high frequency signals between bond pads of an integrated circuit (IC) and an IC tester. The frequency response of the probe card assembly is optimized by appropriately distributing, adjusting and impedance matching resistive, capacitive and inductive impedance values along the signal paths so that the interconnect system behaves as an appropriately tuned Butterworth or Chebyshev filter.

CROSS-REFERENCE TO RELATED APPLICATIONS

[0001] The subject matter of the present application is related to thatof copending U.S. application FILTER STRUCTURES FOR INTEGRATED CIRCUITINTERFACES, Ser. No. ______, (Attorney docket No. 1795 (C81)), filed______, concurrently herewith. The subject matter of the presentapplication is also related to that of copending U.S. applicationINTEGRATED CIRCUIT INTERCONNECT SYSTEM, Ser. No. ______, (AttorneyDocket No. 1796 (C82)) filed concurrently herewith.

BACKGROUND OF THE INVENTION

[0002] 1. Field of the Invention

[0003] The present invention relates in general to a probe card assemblyfor interconnecting test equipment to an integrated circuit die to betested, and in particular to a probe card assembly that implements eachsignal path as a high-bandwidth, low-distortion, impedance-matchedfilter structure between the test equipment and the die.

[0004] 2. Description of Related Art

[0005] An integrated circuit (IC) die typically includes a set of bondpads on its upper surface acting as input/output terminals for theintegrated circuit die, When an IC die is packaged, its bond padsprovide points of connection for bond wires or other structures thatlink the IC to external circuits. These bond pads may also provideaccess points to an IC tester when testing an IC die before it isseparated from a wafer and packaged.

[0006] An IC tester typically includes a separate channel for eachterminal of an IC to be tested, and during a test each channel maytransmit a test signal to the IC terminal or may receive and process anIC output signal appearing at the IC terminal. Each channel is typicallyimplemented on a separate circuit board mounted in a relatively largechassis called a “test head”. The tester normally includes a probe cardassembly for providing signal paths between the circuit boards mountedin the test head and the IC's bond pads.

[0007] PCT published application WO 96/15458, published May 23, 1996(incorporated herein by reference) describes a high performance probecard assembly including a set of three separate layers stackedvertically under the test head. One layer of the assembly, a “probecard” mounted on the probe head, provides points of contact on itssurface for pogo pin connectors extending from the circuit boardsmounted in the test head. The pogo pins act as input and/or outputterminals for the test equipment implemented by those circuit boards. A“space transformer” layer of the probe card assembly includes a set ofprobes on its underside for contacting the bond pads on the uppersurface of the die. An “interposer” board residing between the probecard and the space transformer provides signal routing paths between theprobe card and the space transformer therebetween through springcontacts on its surfaces for contacting pads on facing surfaces of theprobe card and space transformer.

[0008] To test a die at high frequencies it is helpful to position testequipment as closely as possible to the bond pads of the IC being testedso as to reduce the amount of time signals require to travel between thetest equipment and the IC's bond pads. Since the circuit boards in thetest head are much larger than the IC die they are to test, the pogopins through which the circuit boards send and receive signals arenecessarily distributed over a much wider horizontal area than the bondpads on the die being tested. Thus the probe assembly must not onlyroute signals vertically between the bond pads and the pogo pins, italso must also route them horizontally. The probes, pogo pins, springcontracts between the various boards of the assembly, and vias withinthose boards move test signals vertically between the bond pads and thetester circuits. Microstrip traces on the surfaces or layers of thevarious boards of the probe assembly route those signals horizontally.

[0009] One of the reasons tester designers want to minimize the lengthof the signal paths between the bond pads and the circuits is tominimize delay and impedance discontinuities in those signal paths. Whenthose paths carry high frequency test and IC output signals, impedancediscontinuities in the signal path can attenuate and distort thosesignals. The inherent series inductance and shunt capacitance of thesignal routing paths are primary sources of impedance continuities thatcan lead to signal distortion.

[0010] The typical approach to reducing the amount of signal distortionand attenuation caused by the interconnect system has been to minimizesignal path lengths and to match transmission line impedances. In doingso, designers typically try to minimize the physical size of the testercircuits, at least in the horizontal plane, so that they can be packedinto a smaller horizontal space above or below the IC under test. Thisminimizes the horizontal distance that signals must travel between thetest equipment and the IC bond pads they access. Designers also try tominimize signal path lengths in the interconnect system by making theprobe card assembly as thin as possible in the vertical direction, forexample by providing probes and pogo pins that are as short as possible,by making the probe card, interposer and space transformer as thin aspossible, and by providing spring contacts or other contact structuresbetween those boards that are as short as possible.

[0011] Another approach to reducing signal distortion in the signalpaths between IC bond pads and the test equipment accessing them hasbeen to minimize the amount of shunt capacitance in those signal paths.Capacitance can be reduced by appropriately choosing physicalcharacteristics of the probes and the various layers of the probe cardassembly including the size of the traces, their spacing from groundplanes, and the dielectric nature of the insulating material formingthose probe card assembly layers. Since vias, conductors passingvertically through the probe card, interposer and space transformer arealso a source of shunt capacitance, probe card assembly designerstypically structure vias so as minimize their capacitance, typically byproviding a relatively wide hole through any ground or power planethrough which they pass, since the capacitance of a signal path isinversely related to distance between the signal path and any ground orpower planes.

[0012] Minimizing interconnect system signal path lengths, minimizinginductance and capacitances of those signal paths, and matchingtransmission line impedances throughout those signal paths, can helpincrease the bandwidth, flatten frequency response and reduce the signaldistortion. But it is not possible to reduce signal path lengths to zeroor to completely eliminate probe card assembly signal path inductanceand capacitance. Thus some level of signal distortion and attenuation isinevitable when signal frequencies are sufficiently high. Sincedistortion and attenuation increase with signal frequency, such signaldistortion and attention provide a barrier to accurate high frequencytesting.

[0013] What is needed is a way to substantially improve the frequencyresponse of signal paths though a probe card assembly so as to reducedistortion and attenuation of signals below a level that can be providedby simply minimizing the lengths and impedances of those signal paths.

SUMMARY OF THE INVENTION

[0014] The present invention is an improvement to conventional probecard assemblies of the type that interconnect bond pads of an integratedcircuit (IC) die to IC test equipment installed in a test head of anintegrated circuit tester. In accordance with the invention, each signalpath is arranged and adapted to provide a filter function that optimizesrelevant characteristics of the path's frequency response and impedancecharacteristics by appropriately adjusting the magnitudes of its shuntcapacitance and series inductance relative to one another. For examplewhen the test equipment and the die communicate using a low frequencyanalog signal where it is most important to avoid distortion, the“optimal” frequency response of the signal path conveying that signalmay have a narrow, but maximally flat, pass band. Or, as anotherexample, when the test equipment and die communicate via a highfrequency digital signal, the optimal frequency response may have amaximally wide passband. By appropriately distributing and adjusting theinductance and capacitance of a signal path though a probe card assemblyin accordance with the invention, rather than trying to simply minimizethem or treat them as transmission line segments, substantialimprovement in probe card assembly frequency response is obtained.

[0015] It is accordingly an object of the invention to provide a systemfor interconnecting test equipment to terminals of an integrated circuitdevice wherein the frequency response and impedance matchingcharacteristics of the interconnect system are optimized for the natureof signals passing therebetween.

[0016] The concluding portion of this specification particularly pointsout and distinctly claims the subject matter of the present invention.However those skilled in the art will best understand both theorganization and method of operation of the invention, together withfurther advantages and objects thereof, by reading the remainingportions of the specification in view of the accompanying drawing(s)wherein like reference characters refer to like elements.

BRIEF DESCRIPTION OF THE DRAWING(S)

[0017]FIG. 1 is a block diagram of an integrated circuit tester;

[0018]FIG. 2 is a simplified sectional plan view of the test head of theintegrated circuit tester of FIG. 1;

[0019]FIG. 3 is a simplified sectional elevation view of the test headof FIG. 2 and of a probe card assembly in accordance with the inventionfor linking the test head to an integrated circuit device under test(DUT);

[0020]FIG. 4 is an equivalent circuit diagram modeling a single signalpath between one channel of the tester head of FIG. 3 and a bond pad ofa DUT; and

[0021]FIG. 5 compares frequency response characteristics of theequivalent circuit of FIG. 4 when the inductance and capacitance valuesare minimized in accordance with prior art practice (plot A) and wheninductance and capacitance values are adjusted in accordance with thepresent invention.

DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

[0022] The present invention relates to integrated circuit (IC) testersand in particular to an improved probe card assembly for conveyingsignals between bond pads of an integrated circuit device under test(DUT) and the various channels of an IC tester that access the DUTduring a test. FIG. 1 illustrates a typical IC tester 10 in blockdiagram form for performing a test on a DUT 12, suitably in the form ofa die on a silicon wafer 13 that has not yet been separated from thewafer and packaged. An IC die typically includes a set of bond pads onits upper surface that are linked to internal circuit nodes and whichact as input/output terminals for the IC. The bond pads on a die mayprovide points of connection for bond wires linking the circuit nodes topins or legs of an IC package. However when the die is tested before itis packaged, those bond pads may be used as points of contact for probesfrom the tester for conveying signals between the tester and theinternal circuits of the IC.

[0023] Tester 10 includes a set of channels 14, one for each bond pad onDUT 12. During a test, each channel 14 may either generate and transmita digital or analog test signal input to a bond pad of DUT 12 or mayreceive and process a digital or analog DUT output signal deliveredthrough a bond pad. Before the start of the test, a host computer 16transmits instructions to each channel 14 via a bus 18. During the test,a pattern generator within each channel 14 executes those instructionsto produce a sequence of vectors (data values) telling the channel whatto do during successive cycles of the test. At the end of the test,channels 14 send results data back to host computer 14 reporting on thebehavior of the DUT output signals they monitored during the test.

[0024] Channels 14 are implemented on a set of printed circuit boardswhich, in the example tester architecture of FIG. 1, are mounted withinan equipment chassis called a “test head” 20. Channels may also bemounted remote from a test head but linked thereto through transmissionlines. A probe card assembly 22, including the probes that contact thebond pads of DUT 12, provides signal paths between those bond pads andthe circuit boards in the test head implementing channels 14. Moderntesters operating at high frequencies position test head 20 as close aspossible to DUT 12 in order to minimize signal transit time betweentester channels 14 and the IC's bond pads. IC tester designers also tryto minimize the length of the signal paths between the bond pads andchannels 14 in order to minimize the impedance of those signal pathssince signal path impedance can significantly attenuate and distort theDUT input and output signals.

[0025] While the example tester architecture of FIG. 1 is commonlyemployed, many other tester architectures have been used. For example,many testers centralize the pattern generation function of channels 14by providing a central pattern generator to supply data to the channelsduring the test. Also in some testers channels 14 are mounted remotefrom the test head and connected thereto through transmission lines. Theinvention is applicable to all tester architectures.

[0026]FIG. 2 is a simplified sectional plan view of test head 20 of FIG.1 including a set of circuit boards 24 implementing channels 14 ofFIG. 1. FIG. 3 includes a partial sectional elevation view of test head20 of FIG. 2 along with an elevation view of a probe card assembly 22linking circuit boards 24 to bond pads on an IC die (DUT 12) formed on awafer 13. In order to emphasize various parts of the probe card assembly22, FIGS. 2 and 3 are intentionally not to scale. For example, thoseskilled in the art will appreciate, in particular, that test head 20 ismuch wider and taller relative to DUT 12 than is apparent from FIG. 3.

[0027] Since circuit boards 24 implementing channels 14 of FIG. 1 withintest head 20 are much larger than DUT 12 they are to test, channels 14are necessarily distributed over a much wider horizontal area than thebond pads of DUT 12. Thus probe assembly 22 must not only route signalsvertically between the bond pads of DUT 12 and circuit boards 24, italso must also route those signals horizontally. As discussed below,various probes, pogo pins, spring contacts, and vias within variouslayers forming probe card assembly 22 move test signals vertically,while microstrip and stripline traces included within the various layersof the probe assembly 22 route those signals horizontally.

[0028] Designers typically try to minimize the physical size of circuitboards 24, at least in the horizontal plane, so that they can be packedinto a smaller horizontal space above or below DUT 12. This minimizesthe horizontal distance that signals must travel between the testerchannels and the IC bond pads they access. Circuit boards 24 areradially arrayed about a central vertical axis 26 passing through DUT 12below the test head 20 so that all circuit boards 24 are substantiallythe same distance from DUT 12. Each circuit board 24 is suitablyarranged with its signal drivers and receivers mounted near thelower-most corner 28 of the circuit board nearest axis 26. One or morepogo pin connectors 30 extending downward from corner 28 of each circuitboard 24, suitably convey signals between circuit board 24 and probecard assembly 22. By radially arraying circuit boards 24 about centralaxis 26 and positioning their drivers and receivers at corners 28, wehelp minimize the distance that test and DUT output signals must travel.

[0029] Probe card assembly 22, which conveys signals between DUT 12 andthe pogo pins 30 of circuit boards 24, includes a set of threevertically stacked layers. The primary layer of probe card assembly 22,a “probe card” 32, is mounted directly beneath probe head 20. Probe card32 provides points of contact on its upper surface for the pogo pinconnectors 30 that act as input and/or output terminals for the testerchannels 14 implemented by circuit boards 24. A “space transformer” 34includes a set of probes 36 oriented for contacting the bond pads on DUT12. An “interposer” 38 positioned between probe card 32 and spacetransformer 34 includes spring contacts 40 and 42 on its upper and lowersurfaces for providing signal paths between contact pads on the facingsurfaces of probe card 32 and space transformer 34.

[0030] A probe card assembly generally similar to probe card assembly 22of FIG. 3 is described in more detail in PCT published application WO96/15458, published May 23, 1996 and incorporated herein by reference.It should be understood that while the preferred embodiment of theinvention is illustrated herein in connection with the particular probecard assembly architecture described herein, the invention describedherein is also applicable to other kinds of probe card assemblyarchitectures.

[0031] Designers also try to minimize signal path lengths by makingprobe card assembly 22 as thin as possible in the vertical direction,for example by providing probes 36 and connectors 40 and 42 that are asshort as possible and by making probe card 32, space transformer 34 andinterposer 38 as thin as possible. However since there are structurallimitations as to how small, thin and short we can make the variouscomponents of probe card assembly 22, signals must still travel asignificant distance between pogo pins 30 and bond pads on the surfaceof DUT 12, and the impedance of the signal paths they follow distortsand attenuates those signals.

[0032] With signal path distance minimized to the extent possible, thenext step in reducing signal distortion and attenuation in the signalpaths between IC bond pads and the tester channels has been to carefullydesign those signal paths so as to minimize their impedances,particularly their shunt capacitance and series inductance. Thecapacitance of a signal path depends largely on its area, on its spacingand orientation relative to nearby ground and power planes, and on thedielectric constant of the material between the path and those groundand power planes. Thus the capacitance of the signal paths through probecard assembly 22 can be further reduced by appropriately choosingphysical characteristics of probes 36, of contacts 40 and 42, and of thevarious traces and vias within the layers of probe card assembly 22forming those signal paths.

[0033] The series inductance of a signal path is largely a function ofits length, so when we reduce length of a signal path, we also reduceits inductance. However, it is well-known that other physicalcharacteristics of a signal path, such as its width and its spacingrelative to other conductors, can also influence path inductance. Probecard assembly designers have expended considerable effort to furtherreduce the inductance of signal paths through probe card assemblies byappropriately adjusting such physical characteristics of those paths.

[0034] Although minimizing the signal path inductance and capacitancesthrough probe card assembly 22 can generally increase bandwidth andreduce signal distortion, it is not possible to completely eliminatesignal path inductance and capacitance. Likewise it is difficult tomaintain a constant transmission line impedance through the probestructure. Thus some level of signal distortion and attenuation istherefore inevitable. Since distortion and attenuation generallyincrease with signal frequency, such signal distortion and attentionprovide a barrier to accurate high frequency testing.

[0035] The present invention represents a next step in the process ofimproving the frequency response of probe card assembly 22, and tounderstand the invention, it is helpful to first model the signal paththrough probe card assembly 22, and the tester circuits and DUT itinterconnects, with an equivalent circuit diagram. We can then study theeffects on frequency response of various impedance values in the signalpaths provided by a probe card assembly using a conventional circuitsimulator programmed to simulate the frequency response of theequivalent circuit in a well-known manner.

[0036]FIG. 4 is an equivalent circuit diagram of the signal path betweena driver 44 and a receiver 46 within a single tester channel 14 and areceiver 48 and driver 50 linked to a bond pad 52 within DUT 12. Weassume in this example that the DUT terminal being tested is abi-directional input/output terminal, and therefore DUT 12 is depictedas including both a driver 50 for transmitting a DUT output signal frombond pad 50, and receiver 48 for receiving a DUT input signal arrivingat bond pad 52. Tester channel 14 is modeled as an ideal driver 44linked through its output resistance R1, a transmission line (if any)having a characteristic impedance Z0 ₃ and pogo pin 30 to a pad 54 onthe upper surface of probe card 32. The capacitances of pogo pin 30 andof a pad on the surface of probe card 32 for receiving that pogo pin arerepresented by a shunt capacitor C₁. probe card 32 of FIG. 3 includes amicrostrip trace of characteristic impedance Z0 ₃ on one of its surfacesfor routing the signal horizontally from pad 54. Probe card 32 may alsoinclude one or more vias for routing the signal vertically through probecard 32. The capacitances of such vias are included in C₁ and acapacitor C₂. A via also has inductance and resistance, but since itscapacitance predominates, it can be adequately modeled as a single shuntcapacitor.

[0037] Spring connectors 40 and 42 of interposer 38 of FIG. 3 aremodeled in FIG. 4 by a pair of series-connected inductors L₁ and L₂.Interposer 38 includes a vertical via linking connectors 40 and 42, andthe capacitance of that via is suitably represented by a single shuntcapacitor C₃. Space transformer 34 of FIG. 3 includes a microstrip tracefor routing the signal horizontally across one of its surfaces, and thattrace appears in FIG. 4 as characteristic impedance Z0 ₄. A pair ofshunt capacitors C₄ and C₅ represent the capacitance of a contact pad onthe upper surface of space transformer 34 and the capacitance of a viapassing vertically through the space transformer 22. The probe 36 ofFIG. 3 that links the space transformer 22 to bond pad 52 of DUT 12 isprimarily inductive and is suitably represented in FIG. 4 by an inductorL3. The DUT output driver 50 supplies a DUT output signal to bond pad 52through its output resistance R₃ while receiver 48 of DUT 12 receives aDUT input signal arriving at bond pad 52 with an input impedance R₄. DUT12 will typically include an internal electrostatic protection device(ESD) linked to bond pad 52 for protecting DUT 12 from high-voltageelectrostatic noise. The ESD device impedance (mostly capacitive) isrepresented in FIG. 4 by a shunt capacitor C₆.

[0038] The circuit formed by capacitors C1-C6, inductors L1-L3,resistors R1-R4, and transmission line impedances Z0 ₁-Z0 ₄ has areactive impedance that can substantially attenuate and distort signalspassing between driver 44 and receiver 48. As discussed above, theconventional approach to reducing the amount of signal distortion andattenuation has been to minimize to the extent possible the variousseries inductances L1-L3 and shunt capacitances C1-C6 along the path. Itis also a common practice to adjust all of resistances R1-R4 andcharacteristic impedances Z0 ₁-Z0 ₄ to similar values (typically astandardized 50 Ohms in high-frequency applications). Such impedancematching reduces signal reflections, thereby reducing the amount ofdistortion caused by the signal path.

[0039] Table I below lists impedance values of the various componentsFIG. 4 when impedances R₁-R₃ are set to 50 Ohms and all inductances andcapacitances have been set to typical minimum attainable values inaccordance with conventional practice. TABLE I Component Value R₁-R₄ 50Ohms Z0₁-Z0₄ 50 Ohms C₁ 0.4 pF C₂ 0.1 pF C₃ 0.1 pF C₄ 0.1 pF C₅ 0.1 pFC₆ 0.05 pF L₁ 0.8 nH L₂ 0.8 nH L₃ 0.8 nH

[0040]FIG. 5 (plot A) illustrates the frequency response of theinterconnect system model of FIG. 4 when components are set to thevalues indicated in Table I. In particular, FIG. 5 plots signalattenuation as a function of frequency for signals passing from testerdriver 44 to DUT receiver 48. The frequency response for signal passingin the other direction from driver 50 to receiver 46 will be generallysimilar to that shown in FIG. 5 though there will be minor differencesdue to a lack of symmetry.

[0041] The “optimal” frequency response characteristics for theinterconnect system depicted in FIG. 4 depends on the nature of thesignals it is to convey. For example, when DUT 12 communicates via ahigh-frequency digital signal, we may want the interconnect system topass high frequency signals, but we may not be too concerned aboutsignal distortion, and therefore may be able to tolerate a reasonableamount of ripple in the passband. Under such circumstances we would wantthe interconnect system's passband to be as wide as possible while othercharacteristics of the interconnect frequency response are of lesserimportance. On the other hand when DUT 12, for example, communicates viaa low-frequency analog signal, we may want the interconnect system toconvey low frequency signals with little distortion or noise, but we maywant a wide bandwidth. Under such conditions, the optimal frequencyresponse for the interconnect system may include a passband that is asflat as possible but only as wide as needed to pass the highestfrequency signal expected. We would also want all areas of the stopbandto have maximal attenuation so as to block high frequency noise.

[0042] As we see in FIG. 5 (plot A), the passband (usually defined asthe frequency at which attenuation first falls by 3 dB from its level atzero frequency) is about 2 GHz. Thus while the interconnect systemperformance may be acceptable for signals of frequencies ranging between0 and 2 GHz when a maximum 3 dB attenuation is acceptable theinterconnect system frequency response depicted by plot A would not besuitable for conveying signals of frequencies exceeding 2 GHz. We alsonote that the passband is not particularly flat at frequencies above 1GHz. Since passband ripple distorts signals, then in applications wherelow distortion is required, the interconnect system frequency responsedepicted in plot A of FIG. 5 may not be suitable for conveying signalsabove 1 MHz. We further note that the stopband has several large peaksat frequencies above 2 GHz and may therefore fail to sufficientlyattenuate noise at those frequencies. Thus the interconnect system maynot be suitable in applications where we want to greatly attenuate allhigh frequency noise above a certain maximum signal frequency.

[0043] Improved Interconnect System

[0044] According to conventional practice, the frequency response of aprobe card assembly is “optimized” for all applications by minimizingboth its shunt capacitance and series inductance. However while reducinginterconnect system inductance and capacitance generally helps toincrease bandwidth and reduce signal distortion, it is not true thatsetting system inductance and capacitance as low as possible necessarilyoptimizes the frequency response of the system for any particularapplication. In accordance with the invention, system frequency responseis actually improved by increasing the inductance or capacitance of oneor more of the elements forming the signal path through the probe cardassembly above their minimum levels so as to appropriately adjust theirvalues relative to one other.

[0045] Table II compares typical impedance values of the elements ofFIG. 4 set in accordance with prior art practice (Column A) to suitableimpedance selected in accordance with the present invention (Column B)in an application where we want to maximize the passband power. TABLE IIComponent Impedance A Impedance B R₁-R₄ 50 Ohms 50 Ohms Z0₁-Z0₄ 50 Ohms50 Ohms C₁ 0.4 pF 0.4 pF C₂ 0.1 pF 0.7 pF C₃ 0.1 pF 1.3 pF C₄ 0.1 pF 0.5pF C₅ 0.1 pF 1.1 pF C₆ 0.05 pF 0.1 pF L₁ 0.8 nH 0.8 nH L₂ 0.8 nH 0.8 nHL₃ 0.8 nH 0.8 nH

[0046] The impedance values listed Table I are repeated in column A ofTable II. Plot A of FIG. 5 therefore also represents the frequencyresponse of the probe card assembly equivalent circuit of FIG. 4 whenvalues of its circuit components are set in accordance with prior artpractice to typical minimum attainable values as listed in Table II,column A. Plot B of FIG. 5 represents the frequency response of theprobe card assembly equivalent circuit of FIG. 4 when values of itscircuit components are set in accordance with the present invention aslisted in Table II, column B.

[0047] Note that while columns A and B provide the same resistance,characteristic impedance and inductance values, the capacitances listedin column B are somewhat higher than those listed in column A.Conventional wisdom tells us to expect that due to the increase incapacitance values we would expect deterioration in frequency responseas we move from plot A to plot B. For example we would expect plot B toexhibit a narrower bandwidth and/or more ripple in the passband thanplot A. However quite the opposite is true. Note that whereas plot A hasa bandwidth of about 2 GHz, plot B has a substantially wider bandwidth,about 5 GHz. Note also that plot B has relatively less ripple than plotA over all frequency ranges up to about 8 GHz. In accordance with theinvention, the impedance values of column B of Table II were not simplyset to their lowest attainable values, but were instead carefullyadjusted relative to one another and relative to the physical topologyof the interconnect system to optimize the frequency response of theprobe card assembly. In this particular example the values listed inTable II, column B were chosen to maximize the power conveyed in thepassband—that is, to maximize the amount of attenuation integrated overthe full passband range. However other impedance values may be selectedto optimize other characteristics or combinations of characteristics offrequency response for a given application. Thus for example, we mayadjust impedance values to maximize bandwidth, to minimize ripple, toprovide rapid fall off in the stop band, or some combination thereof. Ofcourse we are constrained in our choices for those impedance values;they can be no smaller than the minimum attainable values listed incolumn A of Table I. But subject to that constraint, we have a widelatitude in choosing impedance values that will optimize frequencyresponse of the interconnect system for any given application.

[0048] Thus to optimize the frequency response of the interconnectsystem illustrated in FIG. 4, we first define the frequency responsecharacteristic(s) that we want to optimize. We also determine theminimum practically attainable impedance value for each component of theinterconnect system. We then determine a combination of impedance valuesequal to or larger than those minimum attainable values that willoptimize the desired frequency response characteristics. In the exampleof Table II, column B, it happened that the optimal set of impedanceparameters mandated that inductances be minimized and capacitances beincreased above their minimums. However in other applications, where wewant to optimize other frequency response characteristics, it may bethat inductances could be increased above their minimums. Also asdiscussed below, inductances may be increased in order to compensate forimpedance mismatches.

[0049] Butterworth and Chebyshev Filters

[0050] It is beneficial to think of the equivalent circuit of theinterconnect system illustrated in FIG. 4 as a multiple pole filter. Byappropriately adjusting the series inductance and shunt capacitancesrelative to one another and to the other impedance components of theinterconnect system, the interconnect system can be made to behave, forexample, like a well-known, multi-pole “Butterworth” or “Chebyshev”filter. It is well understood how to adjust the component values of suchfilters in order to obtain a desired frequency response.

[0051] As mentioned above, the frequency response of an interconnectsystem has many characteristics and that its “optimal” frequencyresponse is application-dependent. Thus the appropriate values to whichwe adjust the various impedances along the signals paths of probe headassembly 22 should be adjusted depends on which frequency response andimpedance characteristics are most important for the particularapplication. In the example of Table II, column B, capacitance valueswere chosen to maximize the passband power. However other combinationsof impedance values can optimize other characteristics of theinterconnect system. Thus for example when the interconnect system is toconvey a lower frequency analog signal with minimal distortion, andwhere band width is not so important, it may be desirable that thefrequency response of the interconnect system have a “maximally flat”passband, having the least possible amount of ripple. In such case wewill want to adjust the interconnect system component impedance valuesso that the system behaves like a Butterworth filter which does providea maximally flat frequency response.

[0052] In most applications, however, optimal frequency response will bea tradeoff between the bandwidth, allowable passband ripple, phaseresponse and stopband attenuation. Accordingly the values of inductiveand capacitive components can be selected so that the interconnectsystem behaves as a form of the well-known, multiple-pole Chebyshevfilter. The design of multi-pole Butterworth and Chebyshev filters,including appropriate choices for filter component values so as tooptimize one or more combinations of characteristics of filter'sfrequency response, is well-known to those skilled in the art. See forexample, pages 59-68 of the book Introduction to Radio Frequency Designby W. H. Hayward, published 1982 by Prentice-Hall, Inc., andincorporated herein by reference. Those skilled in the art are wellaware of how to adjust the inductance and capacitance of the variousportions of the various structures along the signal paths provided byprobe head assembly 22 of FIG. 3. The present invention appliesconventional filter design principles to determine how to chose the mostappropriate values for that inductance and capacitance for the intendedapplication.

[0053] Impedance Matching

[0054] Driver and receiver impedances R1-R4, and the varioustransmission line impedances Z0 ₁-Z0 ₄ are typically set to similarvalues (e.g., 50 Ohms) to prevent signal reflections which degradesystem frequency response, and the values for these components werechosen in Table II, column B in order to conform with industry practice.However in accordance with the invention, we need not necessarily dothat because we can compensate for resistive or characteristic impedancemismatch by appropriately adjusting the series inductance and shuntcapacitance values. For example pages 59-68 of the above-mentioned bookIntroduction to Radio Frequency Design illustrate how to adjust otherfilter component values to obtain Butterworth and Chebyshev filterfrequency response behavior even when such resistive and characteristicimpedances are mismatched.

[0055] While the forgoing specification has described preferredembodiment(s) of the present invention, one skilled in the art may makemany modifications to the preferred embodiment without departing fromthe invention in its broader aspects. For example, while in thepreferred embodiment the interconnect system employs bond wires 22 and27 and package legs 24 and 29 to connect nodes of ICs 12 and 14 to PCBtrace 26, other types of inductive conductors, such as for examplespring wires, could be employed to connect nodes of an integratedcircuit to a PCB trace. The appended claims therefore are intended tocover all such modifications as fall within the true scope and spirit ofthe invention.

What is claimed is:
 1. A signal path for linking a node of an electronicdevice to a terminal of an IC tester, the signal path comprising: aprobe for contacting said node; and a conductive path for linking saidprobe to said terminal, wherein said node, said terminal and saidconductive path have impedances sized relative to one another tosubstantially optimize a frequency response characteristic of saidsignal path.
 2. The signal path in accordance with claim 1 wherein saidimpedances include inductances in series with said signal path andcapacitances shunting said signal path.
 3. The signal path in accordancewith claim 1 wherein said conductive path comprises: a probe cardincluding first conductors forming a first part of said conductive path;a space transformer including second conductors forming a second part ofsaid conductive path; and an interposer including third conductors forconveying signals between said first and second conductors, wherein saidimpedances include impedances of said node and of said first, second andthird conductors.
 4. The signal path in accordance with claim 1 whereinsaid frequency response characteristic is one of maximal passband width,maximal passband flatness and maximal passband power.
 5. The signal pathin accordance with claim 1 wherein said impedances are sized relative toone another so that said interconnect system forms a multiple-poleButterworth filter.
 6. The signal path in accordance with claim 1wherein said impedances are sized relative to one another so that saidinterconnect system forms a multiple-pole Chebyshev filter.
 7. A signalpath for linking a node of an integrated circuit (IC) to a terminal ofan IC tester, the signal path comprising: a conductive pad implementedon said IC and linked to said node; a probe for contacting saidconductive pad; and conductive means for linking said probe to saidterminal, wherein said conductive pad, said terminal and said conductivemeans have impedances sized relative to one another to substantiallyoptimize a frequency response characteristic of said signal path.
 8. Thesignal path in accordance with claim 7 wherein said impedances includeinductances in series with said signal path and capacitances shuntingsaid signal path.
 9. The signal path in accordance with claim 7 whereinsaid conductive means includes a printed circuit board via having acapacitance that is one of said impedances.
 10. The signal path inaccordance with claim 7 wherein said conductive means includes a tracehaving a characteristic impedance that is one of said impedances. 11.The signal path in accordance with claim 7 wherein said conductive meansincludes a spring contact having an inductance that is one of saidimpedances.
 12. The signal path in accordance with claim 7 wherein saidconductive means comprises: a printed circuit board via having acapacitance that is one of said impedances, a trace having acharacteristic impedance that is one of said impedances, and a springcontact having an inductance that is one of said impedances,
 13. Thesignal path in accordance with claim 7 wherein said conductive meanscomprises: a probe card including first conductors forming a first partof said signal path; a space transformer including second conductorsforming a second part of said signal path; and an interposer including athird conductor for conveying a signal between said first and secondconductors, wherein said impedances include impedances of said first,second and third conductors.
 14. The signal path in accordance withclaim 7 wherein said frequency response characteristic is one of maximalpassband width, maximal passband flatness and maximal passband power.15. The signal path in accordance with claim 7 wherein said impedancesare sized relative to one another so that said interconnect system formsa multiple-pole Butterworth filter.
 16. The signal path in accordancewith claim 7 wherein said impedances are sized relative to one anotherso that said interconnect system forms a multiple-pole Chebyshev filter.17. A method for sizing impedances of a signal path connecting a node ofan integrated circuit (IC) to a terminal of an IC tester, wherein thesignal path comprises a bond pad connected to said node, a probecontacting said bond pad, and conductive means linking said probe tosaid terminal, the method comprising the step of adjusting impedances ofsaid bond pad, said probe, and said conductive means relative to oneanother so as to optimize a characteristic of a frequency response ofsaid signal path.
 18. The method in accordance with claim 17 whereinsaid characteristic of said frequency response is one of maximalpassband width, maximal passband flatness and maximal passband power.19. The method in accordance with claim 17 wherein said impedances areadjusted such that said signal path acts substantially as amultiple-pole Butterworth filter.
 20. The method in accordance withclaim 17 wherein said impedances are adjusted such that said signal pathacts substantially as a multiple-pole Chebyshev filter.